Voice link over spread spectrum radio
Communication systems using spread spectrum techniques, compare to narrow-band systems are more resistant for noises, signal fading, Doppler effect. Because of code division of signals we can more effective use frequency band and we can increase privacy of transmision. Wide-band systems can be used paralell with narrow-band systems using the same frequency. Process gain allows to reduce output power of transmitter. Major methods used in spread spectrum systems are: Rfequency hopping, time hopping, direct sequence or their hybrids. Spread spectrum signals can support any users signal by conventional analogue or digital modulation. However using AM modulation will destroy signals uniform power spectral density, and it will make more difficult to correlate PN sequence in receiver. Analogue modulated signals are possible to be demodulated without any knowledge of PN code. Frequency modulation is better with frequency hopping spread spectrum. When we use direct sequence spread spectrum, the most suitable will be digital modulation of PN code. We used bipolar phase shift keying.
DSSS link description.
Analogue acoustic signal is converted to digital. Digitalised voice is EX-ORed with digital PN (pseudo-noice) sequence. Modified PN code drives DBM (double balanced mixer) configured as biphase shift keyer. (spreading spectrum). After amplification goes to antenna. In receiver wideband signal arter amplification is EX-Ored with original PN code (despreading spectrum). Narrow-band signal is BPSK modulated. After demodulation, digitalized voice is converted to analog. Main condition is to know PN code, its frequency and phase with precision better than ½ byte.
o synchronisate PN codes three identical channels are used. Except main branch, we have 2 additional branches. Signal in LATE branch is EX-Ored with PN code which is delayed compare to PN code used in main branch about 1 byte. Signal in EARLY branch is EX-Ored with PN code which is earlier than main PN code about 1 byte. When frequency of PN generator in receiver is lower than in transmitter, we receive peak RSSI LATE in LATE branch. When frequency of PN generator in receiver is higher than in transmitter, we receive peak RSSI EARLY in EARLY branch. Both peaks (RSSI LATE and RSSI EARLY) are used to adjust generator VCXO (4MHz) in receiver. So we have PN generators in transmitter and in receiver have identical frequency and phase. Only in this case is posible to despread spectrum and receive narrow-band signal BPSK in receiver.
As a analog to digital (A/D) converter sigma-delta modulator is used. The sampled values of audio signal is compared with staircase approximation of output signal. If the sampled waveform exceeds the staircase approximation, 1 is generated. If the sampled waveform is less than the staircase approximation, 0 is generated. This pulses (0s or 1s) are digitalized voice. When we look at waveform of analog signal, after delta modulator we receive 1s when analog signal increases and we receive 0s when analog signal decreases. When we have constant value or there is no signal, on output of delta-sigma modulator we receive 01010101010101... alternate. At the receiver, the transmitted pulses are integrated and passed through a low-pass filter.
The output of BPSK demodulator does not recover original data polarity. We receive stream of bits identical or inverted compare to original digitalized voice stream in transmitter. In long time transmission, the polarity of digital signal can change a few times, because of disturbations of work of BPSK demodulator. Because as a digital to analog (D/A) converter we use integrator and low-pass filter, change of digital signal from BPSK demodulator causes only change phase of audio output signal. We can not hear it, It is why the polarity recover is no needed in receiver.
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Transmitter block diagram description
Fig.1
The crystal oscillator supplies sinus 16MHz to digital part add sinus 48MHz to make a carrier frequency. Signal 48MHz is multiplied x4 and amplified. Sinus carrier 192 MHz is coming to DBM (double balanced mixer) configured as biphase shift keyer. Carrier is spreaded by modified PN sequence (spreading spectrum). Spreaded signal after amplification goes to antenna.
16MHz signal from crystal oscillator goes to binary divider. After divider we receive 62.5kHz to sampling delta-sigma modulator and 4MHz to provide PN generator. PN generator is made of shift register 74HC164 and EX-OR gates 74HC86. PN sequence is EX-Ored with digitized audio. Modified PN spreading code drives DBM to spread carrier 192MHz. Connecting to GND of inputs of NAND gates causes transmitter generates narrow-band BPSK signal or transmitter generates non modulated carrier 192MHz. Audio signal after amplifier is send to limiter and low-pass filter. Delta-sigma modulator converts audio into serial data stream. This 1-byte A/D converter is made of trigger 74HC74 and operational amplifier configured as comparator. Audio signal in delta-sigma modulator is sampled by 62.5kHz signal taken from binary divider. Binary stream (digitized audio) from delta modulator goes to EX-OR gate to modify PN code.
Detailed description of transmitter
Figure 2: Audio amplifier, limiter and low-pass filter.
Signal from microphone is amplified and next his dynamic is compressed (fig. 2). After amplification by T1 through variable divider signal goes to output amplifier T3 and T4. Divider consist of resistor 22k and T2. It’s attenuation depends on voltage on capacitor 47µ. Output signal from T4 is rectified and charges capacitor 47µ. When amplitude of output signal increases, capacitor 47µ is charged more, and increases attenuation inserted by variable divider (resistor 22k and T2). It causes decreasing amplitude of output signal. When amplitude of output signal decreases, capacitor 47µ is charged less, and decreases attenuation inserted by variable divider . It causes increasing amplitude of output signal. Small - amplitude signals are amplified more than big - amplitude signals. On the output of T4 we have audio signals with approximate constant amplitude. From T4 signal goes to low pass filter made of T5 and T6. It limits audio spectrum up to 3 kHz with decline 8x/oct. Coupling capacitors 0.1µ limit audio spectrum down to about 30 Hz (fig. 2).
Figure 3: Delta-sigma modulator
After limiter and low-pass filter audio signal is amplified by first operational amplifier (fig.3). We adjust resistor 5k6 to reach maximum amplitude of audio signal without distorsions. Second operational amplifier configured as comparator. It compares sampled values of signal with a staircase approximation of output signal (taken from capacitor 0.22µ). We adjust variable resistor 4k7 to minimum distorsions. If the sampled waveform exceeds the staircase approximation (signal increases), from output of comparator is taken „1” to input of trigger 74HC74. If the sampled waveform is less than the staircase approximation (signal decreases), from output of comparator is taken „0” to input of trigger. Signal clock 62.5kHz for sampling is taken from binary divider (showed on fig.4). If there is no audio signal, 1s and 0s are generated alternate. In this case we have digital signal 31.25kHz (fig.3) Delta-sigma modulator converts audio into serial data stream which goes to digital part of transmitter (showed on fig.4).
Fig. 4
Signal from 16MHz generator (from fig. 5) after buffer (first NAND gate) goes to binary divider 74HC4040. After dividing by 256 we receive signal 62,5 kHz for sampling audio (in delta-sigma modulator fig. 3). 16 MHz after dividing by 4 is 4 MHz to drive PN (pseudo noise) generator. Generator PN is made of 8-stage shift register 74HC164 and EX-OR gates 74HC 86 in feedback circuit. We use 7 registers. It allows to generate PN code of 127 bytes length. PN sequence goes to second NAND gate. Connecting to GND of its second input causes transmitter generates narrow-band BPSK signal. PN sequence (if second input of NAND gate is not grounded) goes to EX-OR gate. To the second input of this EX-OR gate goes binary stream (digitized audio) from delta modulator (showed on fig. 3). This EX-OR gate modifies PN sequence in this way: it inverts PN sequence if digitized audio value is „1”. If digitized audio value is „0”, passes PN code with no changes. Modified PN sequence goes to third NAND gate. Connecting to GND of its second input causes transmitter generates non modulated carrier. Both switches S1 and S2 can be helpful during testing. Using S2 and generate carrier only helps to adjust RF part of transmitter and downconverter in receiver. Using S1 (S2 not used) we have narrow-band BPSK signal which may help to adjust BPSK demodulator in receiver. Fourth NAND gate configured as inverter inverts modified PN sequence. Both signals „WY” and „/WY” through resistors k68 drive double balanced mixer configured as BPSK modulator (showed on fig.5).
Fig. 5
Oscillator with T1 (fig. 5) is stabilized by crystal Q=16 MHz. From emiter of T1 signal 16 MHz goes to amplifier-limiter with T5. From its output square - wave signal 16 MHz goes to buffer before binary divider in digital part (showed on fig. 4). LC circuit in collector of T1 is tuned to frequency 48 MHz. This signal goes to multiplier x4 with T2. LC circuit in collector of T2 is tuned to frequency 192 MHz. From its output signal is taken to buffer 192 MHz with T3. Sinus signal 192 MHz (carrier) is phase modulated by double balanced mixer configured as BPSK modulator. (spreading spectrum by modified direct PN sequence). Double balanced mixer is driven through resistors k68 by signals „WY” and „/WY” from digital part (showed on fig. 4). On the output of mixer we have signal with spread spectrum. 90% of its energy has bandwidth 8 MHz: from 188 MHz to 196 MHz (carrier frequency +/- clock frequency of PN generator). SS signal through buffer with T4 goes to output. This signal can be amplified by power amplifier (not showed). Power amplifier must have bandwidth minimum 8 MHz.
Description of receiver
Transmisja dźwięku z wykorzystaniem widma rozproszonego.
How to receive signal
Signal with spread spectrum has pseudo-noise character and large spectrum. Using normal receiver even with ten same frequency band, we receive only higher noise level, no signal. It is impossible to try manually find any station. The receiver for spresd spectrum systems is much more complicated than narrow-band receiver.Receiver must to know:
To receive right frequency (a.) we adjust frequency of quartz used in crystal generator in heterodyne of receiver. When we build PN generators in receiver and transmitter according to the same schematic diagram, we will have identical PN sequences in transmitter and receiver (b.). By adjusting clocking generators for PN generators in receiver and transmitter we have almost the same frequencies of PN sequences (c.).
Synchronization
The most difficult problem in Spread Spectrum systems is synchronization of PN sequences in transmitter and receiver (d.). Only when PN sequences in receiver and transmitter have the same phase, it is possible to despread spectrum of signal. (spectrum of signal was spread in transmitter). We have some options:
In first option (a.) additional with modulated and spread carrier (user’s signal) is sent no modulated, only spread carrier (reference signal). In receiver both signals (amplified) go to 2 inputs of double balanced modulator, and we receive user´s signal. In receiver there is no PN generator. In transmitter we have additional branch to transmit reference signal. In this case we of course no need to know PN code.
In other method (b.) frequencies of PN generators in receiver and transmitter are synchronized by other external signals. We can use local MW broadcast radio, TV synchro-signals, or DCF77 or other. In this case we must manually adjust phase of PN sequence (once at beginning of transmission). Transmitter and receiver must have modules for receive external signals.
The most critical and most difficult is method (c.), without additional signals. In this case transmitter is less complicated, and receiver is most complicated. Receiver must receive right frequency, and must find moment of synchronization, fine adjust frequency of PN generator, hold phase of PN sequence, When phases of PN sequences in transmitter and receiver are different more than ½ byte (too early or to late), synchronization circuit must correct frequency of PN generator (decrease or increase). We adjust crystal generators in transmitter and receiver to the same frequency, but their frequencies are little difference. It is why phase of PN sequence in receiver is changing (compare to transmitter). Every some seconds (time depends on difference in frequencies) we have identical phases of PN sequences. In this moments spectrum of received signal is despreaded. On output of receiver we have higher level of signal (impulse). This impulses we use to find moments of synchronization.
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How to hold right phase
We need 2 information about phase of PN sequence in receiver: phase is earlier more than ½ byte (decrease frequency) phase is late more than ½ byte (increase frequency)Add to our circuit despreading spectrum 2 identical branches more. Difference is only in phase of PN sequences given to each branch (to input of double-balanced mixer). In EARLY branch, phase of PN sequence is earlier about ½ byte. In LATE branch, phase of PN sequence is later about ½ byte than phase in ON-TIME branch. If frequency of PN generator in receiver becomes higher, we will have impulse in EARLY branch. If frequency of PN generator in receiver becomes lower, we will have impulse in LATE branch. Both impulses are used to adjust (decrease or increase) frequency of PN generator in receiver. If this generator is not connected to frequency adjusting circuit, we will have RSSI impulses appearing in EARLY, ON-TIME, LATE branches or reverse order. It depends on which PN generator (in transmitter or in receiver) has higher frequency.
Receiver block diagram description
receiver set (soon)
Fig.2
Fig. 3
Fig.4
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Fig . 7
Go to Transmitter
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